Semiconductor integrated circuit device and wireless communication system

ABSTRACT

The dynamic range is changed by switching a current applied to an amplifying circuit to obtain the minimum ICP required to keep linearity with the number of multiplexes even when the number of multiplexes of data is changed by switching the operation current of the amplifying circuits of the transmission system and also supplying the information about number of multiplexes of data to be transmitted to the amplifying circuits of the transmission system from the baseband circuit. Thereby, the signal can be transmitted without distortion even when the number of multiplexes increases and the current of the amplifying circuit may be reduced when the number of multiplexes is small in order to reduce the current consumption in the communication semiconductor integrated circuit device which can form a wireless communication system of the code division multiplex system such as W-CDMA system.

The present application is a continuation of application Ser. No.10/685,481, filed Oct. 16, 2003, the contents of which are incorporatedherein by reference.

BACKGROUND OF THE INVENTION

The present invention relates to a wireless communication technology,more specifically to a technology which may be effectively applied,while increase of power consumption is controlled, for improvinglinearity of a semiconductor integrated circuit device comprising anamplifying circuit to amplify the code division multiplexed transmittingsignal. Moreover, the present invention relates to a technology whichmay be effectively applied to a semiconductor integrated circuit devicefor communication constituting a wireless communication device, forexample, of W-CDMA (Wideband Code Division Multiple Access) system andto a wireless communication device such as a mobile telephone or thelike comprising the same semiconductor integrated circuit device.

In the wireless communication device such as a mobile telephone (mobilecommunication device), a multiplex system is employed to increase theamount of data to be transmitted. The present multiplex system used forthe mobile telephone includes a TDMA system (time division multiplexsystem) and a CDMA system (code division multiplex system) or the like.The CDMA system is a communication system where a plurality of diffusedcodes having orthogonality in the same frequency space are used forspectrum diffusion of carrier and the diffused carriers are assigned toa plurality of channels. The CDMA system is employed for the mobiletelephone of the W-CDMA system. In the mobile telephone of the PDC(Personal Digital Cellular) system and GSM (Global System for MobileCommunication) system, the TDMA system is employed.

In the mobile telephone of W-CDMA system, the I, Q signals generatedbased on the transmission data in a baseband circuit are supplied to atransmitting circuit including a modulation circuit, the signalsobtained by modulating a local oscillation signal with the I, Q signalsare supplied to a power amplifier for the power amplification andfinally the amplified signals are outputted from an antenna. For themobile telephone of the W-CDMA system, there is provided a system wherelevel and accuracy of an average output power corresponding to theoutput request level transmitted from a base station are determined bythe specification, gain of a power amplifier is controlled with anoutput control signal supplied from the baseband circuit, and signalsare transmitted in the specified output power.

SUMMARY OF THE INVENTION

In the specification of the mobile telephone of the W-CDMA system, it isspecified that the data of six channels in maximum can be transmittedfrom one channel through the multiplexing, but this method has problemsthat the more the number of multiplexes of data is increased, the morethe distortion of transmission signal increases and thereby the ACPR(leak power ratio to the adjacent channel) characteristic isdeteriorated. Therefore, the inventors of the present invention haveinvestigated causes of these problems. As a result of the investigation,it has become apparent that the number of multiplexes of data is closelyrelated to peak factor and the peak factor becomes larger as the numberof multiplexes increases. Here, the peak factor is a difference betweenthe maximum peak value of the transmission signal (momentary maximumpower) and an average output level.

FIGS. 13(A) and 13(B) illustrate waveform images of the transmissionsignals when the number of multiplexes is “1” and “6” in the W-CDMAsystem. In these FIGS. 13(A) and 13(B), “ave” is an average output levelwhich is determined with an output control voltage. In the specificationof the mobile telephone of the W-CDMA system, even when the averageoutput level ave is identical as illustrated in FIGS. 13(A) and 13(B),the peak factor when the number of multiplexes is “6” becomes largerthan that when the number of multiplexes is “1”. FIG. 14 illustrates therelationship between the number of multiplexes and peak factor in themobile telephone of the W-CDMA system. From FIG. 14, the peak factor isabout 3 dB when the number of multiplexes is “1”, but it increases up to7.5 dB when the number of multiplexes is “6”.

Moreover, it has been found when the transmission signal is amplifiedwith an amplifying circuit having a narrower dynamic range with the peakfactor which is large as described above, distortion of signal increasesand the ACPR characteristic is deteriorated. Therefore, the inventors ofthe present invention have thought to design an amplifying circuithaving wider dynamic range to amplify the transmission signal in orderto obtain the IPC (1 dB Compression Point) for transmission of signalwithout distortion even when the maximum number of multiplexes is “6”.

It is generally known that a wide dynamic range of the amplifyingcircuit can be obtained by increasing a current flowing into thecircuit. However, since power consumption of the total system increaseswhen the current of the amplifying circuit increases, it is a problem tobe eliminated as much as possible in the system such as a mobiletelephone which is operated with a battery. Particularly, since thetransmitting operation is executed separately from the receivingoperation in the mobile telephone of the time division multiplex systemlike a PDC, the current consumption is not so large. However, in themobile telephone of the W-CDMA system, since the transmitting operationand receiving operation are executed simultaneously and continuously,current consumption is considerably larger than that of the mobiletelephone of the PDC system. Therefore, increase in current of theamplifying circuit in the mobile telephone of the W-CDMA system willresult in the problem that the maximum communication time and themaximum waiting time which are intrinsically short may be furthershortened.

As the prior art of the present invention, there is the JapanesePublished Unexamined Patent Application No. 270733/1997. This prior artis intended to realize low power consumption by changing accuracy ofarithmetic operations of a band-pass filter depending on the informationabout number of channels to be multiplexed. Therefore this prior artseems to be similar to the present invention when attention is paid toreduction of power consumption by switching the circuits based on theinformation about the number of multiplexes of the signals.

However, the present invention relates to a mobile telephone but thisprior art relates to a transmitter in the base station side. Moreover,in the present invention, the information used for control is the numberof multiplexes of data to be transmitted, while such data is the numberof multiplexes of channel, namely the number of mobile terminals forcommunication in the prior art. In addition, the control object circuitto be switched is the dynamic range of a differential amplifier (analogcircuit) in the present invention but it is the number of taps in theband-pass filter (digital filter) in the prior art. Therefore, the priorart is the invention which is obviously different from the presentinvention.

An object of the present invention is to realize, in a wirelesscommunication system which performs multiplexing of signals withspectrum diffusion such as a W-CDMA system, that a signal can betransmitted without distortion even when the number of multiplexes isincreased and a current of an amplifying circuit can be reduced toresult in lower current consumption when the number of multiplexes issmall and thereby the operation life of a battery, namely the maximumcommunication time and the maximum waiting time based on the singlecharging cycle can be extended considerably when the present inventionis applied to a mobile telephone.

Another object of the present invention is to provide a semiconductorintegrated circuit device for communication to form a wirelesscommunication system of the code division multiplex system which canimprove the ACPR (leak power ratio to the adjacent channel)characteristic, and to provide a wireless communication system using thesame semiconductor integrated circuit device.

The aforementioned and the other objects and novel features of thepresent invention will become apparent from description of the presentspecification and the accompanying drawings.

First, a problem in the transmission system of the mobile telephone ofthe W-CDMA system to which the attention of the inventors has been paidand a method of solving the problem of the present invention will bedescribed.

In the W-CDMA transmission system, the signals (sin wave and cos wave)of the predetermined frequency in the phases with difference of 90° aresubjected to the BPSK modulation with the control data DPCCH and userdata DPDCH to generate I and Q signals, and these signals are diffusedin the spectrum with the channelization code in the rate of 3.84 Mcps.When the user data DPDCH is “0”, the I signal modulated only with thecontrol data DPCCH is generated and this signal is spectrum-diffused.When the user data DPDCH is “3”, the control data DPCCH and one of theuser data, for example, DPDCH2 are assigned to the Q signal. Moreover,the remaining two data DPDCH1, DPDCH3 of the user data are assigned tothe Q signal for modulation. Thereafter, the signal isspectrum-diffused. Generation of the I signal and Q signal, namelymultiplex described above is performed in the circuit called thebaseband circuit.

FIGS. 12(A) and 12(B) illustrate constellations indicating, on the IQcoordinates, position and changing direction of each symbol of thesignal generated by the code division diffusing process (multiplex)performed by the baseband circuit. FIG. 12(A) corresponds to theconstellation when the number of multiplexes is “1”, while FIG. 12(B)corresponds to the constellation when the number of multiplexes is “6”.From these figures, it is obvious that the probability for passing theorigin when the number of multiplexes is “1” is higher than that whenthe number of multiplexes is “6”. Here, since the fact that a symbolshifts to the other symbol passing the origin means that the phasechanges for 180°, amount of protrusion to the external side from theposition of the target symbol becomes larger than that of the othercase. Increase in amount of protrusion is a cause of enlargement of thepeak factor of the transmission signal as illustrated in FIGS. 13(A) and13(B).

In the W-CDMA system, diffusion is executed twice as specified in thespecification, but the HPSK modulation is performed when the seconddiffusion is executed. Accordingly, probability for passing the originin the IQ constellation may be reduced, the peak factor may be keptsmall and the linearity required for transmitting circuit may also bealleviated. However, when the number of multiplexes, namely the numberof user data DPDCH increases, effect of the HPSK modulation is lowered.Therefore, it is thought that probability for passing the origin in theconstellation increases and thereby the peak factor is increased.

FIG. 14 illustrates the relationship between the number of multiplexesand the peak factor in the transmission signal of W-CDMA system in theform of a graph based on the simulation and actually measured values.From FIG. 14, it is known that the peak factor increases rapidly whenthe number of multiplexes exceeds “3”. Therefore, when the peak factorbecomes large, since distortion of signal becomes large when thelinearity of circuit to transmit the signal is not sufficient, thelinearity of the transmission circuit must be improved.

As an index indicating linearity of circuit, an index called IPC (1 dBcompression point) which indicates characteristic for transmissionwithout distortion of signal is used. Hereinafter, this index is used inthe description. Moreover, since it is known that the third orderintercept point IP3 and saturation power Psat are also related to theICP to a certain degree, the ICP in the description of the specificationmay be replaced with IP3 or Psat.

For transmission of a multiplex signal without any distortion, the rangeof linear characteristic of the transmission circuit, namely the dynamicrange is generally widened as much as the peak factor. Namely, thesignal can be amplified without distortion even when the number ofmultiplexes is “6” by designing a circuit of variable gain amplifyingportion enough to accept the maximum level (maximum peak factor) to beinputted to the circuit. In more practical, it is understood from FIG.14 that the peak factor when the number of multiplexes is “6” isincreased by about 4.5 dB in comparison with the case where the numberof multiplexes is “1”. Therefore, when the ICP of the circuit isimproved by 4.5 dB, deterioration of distortion characteristic due toincrease in the number of multiplexes can is be eliminated.

However, the maximum peak voltage which is a factor of peak factor iscomparatively small and appears in average when the number ofmultiplexes is small as can be understood from FIG. 13(A), but when thenumber of multiplexes increases, the maximum peak voltage is no longeraverage and appears at random in the large value and small value withless appearing frequency of the comparatively large value as can beunderstood from FIG. 13(B). Accordingly, it is most desirable that IPCof the transmission circuit is improved by 4.5 dB in accordance with thepeak factor. However, it is thought enough for practical use when theIPC is improved by about 3 dB.

FIG. 15 illustrates relationship between a current and 1 dB compressionpoint ICP in the variable gain amplifying portion of a general codedivision multiplex transmission circuit in the mobile telephone of theW-CDMA system. From FIG. 15, it can be understood that the ICP can beincreased by 3 dB by increasing a current of the variable gainamplifying portion by 100%.

On the other hand, there is provided a leak power ratio of adjacentchannel ACLR as the specification to indicate distortion of the circuitin the W-CDMA transmission system. FIG. 16 illustrates relationshipbetween the 1 dB compression point ICP and leak power ratio of adjacentchannel ACLR in the variable gain amplifying portion of the ordinarycode division multiplex transmission circuit of the W-CDMA system. FromFIG. 16, it can be understood that the leak power ratio of adjacentchannel ACLR can be improved by 6 dB by improving the 1 dP compressionpoint ICP indicating the linearity of the circuit by 3 dB.

However, when the circuit is designed to operate the transmissioncircuit after it is fixed to the bias point which makes sufficient theICP and ACLR like the point A′ in FIG. 16 and the point B′ in FIG. 15,the transmission signal is never distorted even when any signal isinputted and stable ACLR characteristic can be obtained. However, inthis case, the current consumed by the circuit becomes always largewithout relation to the input signal.

The data transmitted in the W-CDMA system becomes 384 kbps in maximumwhen the number of multiplexes is “1” and 2 Mbps in maximum when thenumber of multiplexes is “6”. However, the multiplexing is no longerrequired during communication by voice and during transmission of textdata such as mails and the number of multiplexes is considered to beenough when it is “1”. Increase in number of multiplexes is necessaryonly for transmission of moving image data, transmission of personalcomputer data and transmission of a large amount of data used in theInternet. Namely, the average amount of data transmitted from a mobiletelephone is rather smaller than the maximum amount and it is not alwaysrequired to set the number of multiplexes to “6”. From such point ofview, it is useless to always allow continuous flow of large current inorder to attain linearity of the circuit in the conditions of recentyears that the longer maximum waiting time and maximum communicationtime are required for the mobile telephone.

Therefore, in the present invention, an operation current of anamplifying circuit of the transmission system may be switched and theinformation about the number of multiplexes of data to be transmitted issupplied to the amplifying circuit of the transmission system from thebaseband circuit. Thereby, change of current is controlled so as to makethe current flow, to the amplifying circuit, for obtaining the minimumIPC required to keep linearity in the number of multiplexes even whenthe number of multiplexes of data changes.

According to the means described above, since dynamic range can bevaried without almost changing gain of the amplifying circuit bychanging a current flowing into the amplifying circuit, the signal canbe transmitted without distortion by widening the dynamic range when thenumber of multiplexes is large and moreover current consumption can belowered by reducing the current of the amplifying circuit when thenumber of multiplexes is rather small. In addition, since the 1 dBcompression point ICP in the variable gain amplifying portion of thetransmission circuit can be improved, the ACPR (leak power ratio toadjacent channels) characteristic can also be improved.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is a block diagram showing a first embodiment of a transmissionsystem circuit of a mobile telephone of the W-CDMA system to which thepresent invention is applied.

FIG. 2 is a block diagram showing a second embodiment of thetransmission system circuit of the mobile telephone of the W-CDM systemto which the present invention is applied.

FIG. 3 is a block diagram showing a third embodiment of the transmissionsystem circuit of the mobile telephone of the W-CDMA system to which thepresent invention is applied.

FIG. 4 is a timing chart showing the transmission timing of a controlsystem signal between a baseband circuit and the transmission systemcircuit in the mobile telephone of the embodiment of FIG. 3.

FIG. 5 is a circuit diagram showing a practical example of a variablegain amplifying circuit which can vary the dynamic range and a currentswitching circuit in the transmission system circuit.

FIG. 6 is a circuit diagram showing another example of the variable gainamplifying circuit which can vary the dynamic range.

FIG. 7 is a circuit diagram showing a practical example of the gainvariable amplifying circuit in the transmission system circuit.

FIG. 8 is a circuit diagram showing the other example of the gainvariable amplifying circuit.

FIG. 9 is a block diagram showing a fourth embodiment of thetransmission system circuit of the mobile telephone of the W-CDMA systemto which the present invention is applied.

FIG. 10 is a circuit diagram showing a practical example of a powermodule in the mobile telephone of the embodiment of FIG. 9.

FIG. 11 is a circuit diagram showing the other example of the powermodule in the mobile telephone of the embodiment of FIG. 9.

FIGS. 12(A) and 12(B) are the constellation diagrams indicating, on theIQ coordinates, the position and changing direction of each symbol ofthe signal generated by the code division diffusing process(multiplexing) performed in the baseband circuit.

FIGS. 13(A) and 13(B) are waveform diagrams showing waveform images ofthe transmitting signal when the number of multiplexes is “1” and “6” inthe W-CDMA system.

FIG. 14 is a graph showing relationship between the number ofmultiplexes and peak factor in the mobile telephone of the W-CDMAsystem.

FIG. 15 is a graph showing relationship between a bias current and 1 dBcompression point ICP in the variable gain amplifying portion of thecode division multiplex transmission circuit of the mobile telephone ofthe W-CDMA system.

FIG. 16 is a graph showing relationship between 1 dB compression pointICP and leak power ratio of adjacent channels ACLR in the variable gainamplifying portion of the code division multiplex transmission circuitof the mobile telephone of the W-CDMA system.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

The preferred embodiments of the present invention will be describedwith reference to the accompanying drawings.

FIG. 1 illustrates an embodiment when the present invention is appliedto a code division multiplex transmission circuit of a mobile telephoneof the W-CDMA system.

As illustrated in FIG. 1, the mobile telephone of this embodimentcomprises an antenna 110, a power module 120, a code division multiplextransmission circuit 130, and a baseband circuit 140. In view ofsimplifying the figure, a low noise amplifying circuit (LNA), a filter,an isolator, a coupler and a frequency synthesizer are not illustratedin the figure but these are naturally provided as required.

Although not restricted particularly, the code division multiplextransmission circuit 130 and baseband circuit 140 are formed, in thisembodiment, on a semiconductor chip as a semiconductor integratedcircuit device (RF-IC and baseband IC). Moreover, the power module 120is formed as a semiconductor transistor for power amplification, asemiconductor integrated circuit in which a bias circuit is formed togive a bias to the transistor described above and an electroniccomponent where a coupler is mounted on an insulated substrate such asceramic. However, this power module may also be formed on onesemiconductor chip as a semiconductor integrated circuit. In addition,although not illustrated in FIG. 1, a receiving circuit to amplify andmodulate the signal received from the antenna 110 may be formed on thesame chip as the semiconductor chip where the code division multiplextransmission circuit 130 is formed.

As illustrated in FIG. 1, the code division multiplex transmissioncircuit 130 of this embodiment includes a modulating portion 131, afirst variable gain amplifying portion 132, a first local oscillator133, a second local oscillator 134, a frequency conversion circuit 135consisting of a mixer, and a second variable gain amplifying portion136. In the code division multiplex transmission circuit 130, the I, Qsignals outputted from the baseband circuit 140 are inputted to themodulating portion 131 which provides outputs through modulation of thelocal oscillation signal with the I and Q signals.

The first variable gain amplifying portion 132 amplifies the signalmodulated in the modulating portion 131 and adjusts an average outputlevel depending on the gain control signal Vapc from the basebandcircuit 140. The frequency conversion circuit 135 inputs an output ofthe first variable amplifying portion 132 and an oscillation signal ofthe second local oscillator 134, and performs frequency conversion(up-conversion). The second variable amplifying portion 136 amplifies anoutput of the frequency conversion circuit 135 and then outputs theamplified signal to the power module 120. The second variable gainamplifying portion 136 also adjusts the average output level dependingon the gain control signal Vapc from the baseband circuit 140. Moreover,the power module 120 amplifies an output of the second variable gainamplifying portion 136 and then transmits the transmission signal fromthe antenna 110. The power module 120 also adjusts the average outputlevel depending on the gain control signal Vapc from the baseband 140.

Here, the transmission signal outputted from the variable gainamplifying portions 132, 136 vary the peak factor depending on thenumber of the code division multiplexes of the I and Q signals outputtedfrom the baseband circuit 140. As described above, when the number ofmultiplexes increases, the maximum peak power becomes large although theaverage power does not change. This change of the maximum peak powerwill result in distortion of signal.

A base station which receives a transmission signal transmitted from theantenna 110 generates an output level instruction command TPC to set thesignal level to the predetermined level depending on the averagereceiving level and then transmits this TPC signal. In the mobiletelephone side, the baseband circuit 140 generates a gain control signalVapc depending on this command and then supplies this gain controlsignal Vapc to the power module 120 and transmission circuit 130.However, since any attention is not paid to the maximum peak power, thesignal of the transmission circuit 130 is distorted.

Therefore, in this embodiment, the variable amplifying portions 132 and136 are configured to enable the switching of the operation currents,the control information MC of three bits indicating the number of codedivision multiplexes is supplied to the transmission circuit 130 fromthe baseband circuit 140, and the operation currents of the variablegain amplifying portions 132 and 136 are switched depending on thiscontrol information MC. In more practical, the operation currents ofboth first variable gain amplifying portion 132 and the second variablegain amplifying portion 136 or the operation current of any one thereofis switched so that when the number of multiplexes is small, theoperation current decreases and when the number of multiplexes is large,the operation current increases.

Thereby, IPC, namely dynamic range of the variable gain amplifyingportions 132, 136 is varied, the signal is amplified without distortionof signal and low current consumption may be attained. Amount of changeof current due to the switching of the operation current is not linearfor the number of multiplexes and is determined depending on therelationship between peak factor and number of multiplexes of FIG. 14.In other words, setting is made to provide the largest change while thenumber of multiplexes is within the range to “4” from “2”. The variablegain amplifying circuit which can switch the operation current will bedescribed later. In this embodiment, the control information MCindicating the number of multiplexes is given to the transmissioncircuit 130 as the code of three bits from the baseband circuit 140, butit may be given as the control voltage which takes any voltage level ofseven levels.

FIG. 2 illustrates the second embodiment where the present invention isapplied to a code division multiplex transmission circuit of a mobiletelephone of the W-CDMA system. In the transmission circuit of the firstembodiment, the transmission signal is up-converted in two stages up tothe desired frequency using oscillation signals of two local oscillators133, 134, while in the transmission circuit of this second embodiment,the transmission signal is quickly up-converted up to the desiredtransmission frequency using the oscillation signal of one localoscillator 133.

Moreover, in this second embodiment, the average output levels of thevariable gain amplifying portion 132 and power module 120 is adjusteddepending on the gain control signal Vapc from the baseband circuit 140,the control information MC indicating the number of code divisionmultiplexes is supplied to the transmission circuit 130 from thebaseband circuit 140, and the operation current of the variable gainamplifying portion 132 is switched depending on the control informationMC. Even in this embodiment, the control information MC indicating thenumber of multiplexes may be any one of the 3-bit code or the controlvoltage of seven voltage levels.

FIG. 3 and FIG. 4 illustrates a third embodiment when the presentinvention is applied to the code division multiplex transmission circuitof the mobile telephone of the W-CDMA system. This embodiment isdifferent from the first embodiment only in the method of applying thecontrol information MC indicating the code division multiplexes given tothe transmission circuit 130 from the baseband circuit 140, and isidentical to the first embodiment in the point that the operationcurrents of the variable gain amplifying portions 132, 136 are switcheddepending on the control information MC indicating the number ofmultiplexes.

In more practical, the transmission circuit 130 of the third embodimentis provided with a mode control circuit 137 which controls the interiorof the RF-IC chip such as power ON/OFF of the transmission circuit andsetting of frequency of the local oscillators 133, 134 depending on themode control signal for designating each operation mode supplied fromthe baseband circuit 140. The mode control circuit 137 and the basebandcircuit 140 are connected with three signal lines. One of the threesignal lines is a signal line to supply the clock signal CLK, anothersignal line is used for serial transfer of the data DATA and theremaining signal line is used to supply the load enable signal LE whichallows fetching of the data.

The mode control circuit 137 of this embodiment is provided, althoughnot particularly restricted, with a 10-bit shift register and a 10-bitcontrol register. The serial data DATA is fetched by the shift resistorand is then shifted in synchronization with the clock CLK supplied fromthe baseband circuit 140 in the timing shown in FIG. 4 and the data ofshift register is latched simultaneously to the control register insynchronization with the fall of the load enable signal LE. In FIG. 4, abroken line given to the load enable signal LE indicates that the datafetched by the shift register in this period is valid.

In this embodiment, the 3-bit control information MC indicating thenumber of multiplexes is supplied to the transmission circuit 130 fromthe baseband circuit 140 using three signal lines connecting between themode control circuit 137 and baseband circuit 140. In this case, thecontrol information MC indicating the number of multiplexes is alsogiven the code indicating that it is the multiplex number informationand it is also transmitted together. Accordingly, the mode controlcircuit 137 extracts the control information MC indicating the number ofmultiplexes from the data fetched by the shift register and then givesthis control information MC to the variable gain amplifying portions132, 136.

Next, a practical circuit example of the amplifying circuit which canvary the operation current, namely dynamic range will be disclosed.

FIG. 5 is an example of the amplifying circuit consisting of a bipolartransistor. The amplifying circuit of this embodiment is formed of apair of input differential transistors Q1, Q2, a resistor Re0 connectedbetween the emitters of the transistors Q1, Q2, collector load resistorsRc1, Rc2 connected between the collectors of transistors Q1, Q2 and thepower supply voltage terminal Vcc, a differential amplifying stageconsisting of constant current transistors Q3, Q4 connected between theemitters of the transistors Q1, Q2 and the grounding point, and acurrent switching circuit 138 for switching the currents of the constantcurrent transistors Q3, Q4.

The current switching circuit 138 is formed of a transistor Q5current-Miller connected with the constant current transistors Q3, Q4, aconstant current source CCS, a transistor Q10 connected in series to theconstant current source CCS between the power supply voltage terminalVcc and the grounding point, ransistors Q11, Q12, Q13 current-Millerconnected to the transistor Q10, switching MOSFETs Q21, Q22, Q23connected in series to these transistors Q11, Q12, Q13, and a decoderDEC for generating the ON/OFF control signal impressed to the gateterminals of the switching MOSFETs Q21, Q22, Q23 by decoding the 3-bitcontrol information MC indicating the number of multiplexes suppliedfrom the baseband circuit 140.

Q1 to Q5 of the transistors are NPN transistors, while Q10 to Q13 arePNP transistors, Q3 to Q5 are connected with emitter resistors Re1 toRe3, and Q10 to Q13 are connected with emitter resistors Re4 to Re7.Moreover, the transistors Q11 to Q13 form a current adding circuit withcommon connection of collectors and a current added with this addingcircuit is applied to the transistor Q5 as a collector current.

The amplifying circuit of this embodiment is configured to change inseven levels the current of the constant current transistors Q3, Q4 byswitching the current flowing into the transistor Q5 with the 3-bitcontrol information MC. Moreover, the current of the constant currenttransistors Q3, Q4 may be varied not depending on the constant changingrate but depending on the characteristic curve of FIG. 14, by adequatelysetting the combination of an emitter size ratio of the transistors Q10to Q13 and the MOSFETs Q21 to Q23 which are turned ON with the controlinformation MC.

The amplifying circuit of this embodiment is expressed asgmQ1=1/(reQ1+RE)  (1)

when a resistance value of emitter resistor Re0 of the inputdifferential transistors Q1, Q2 is RE, a resistance value of collectorresistor Rc1 is RL, a mutual conductance of the input differentialtransistor Q1 is gmQ1 and an operation resistance when the collectorcurrent Iee is flowing is reQ1.

Therefore, gain G1 is expressed as follows.G1=gmQ1·RL=RL/(reQ1+RE)  (2)

Here, since the operation resistance re of a bipolar transistor isexpressed as re=2 kT/ql when k is the Bortzman's constant, q is amountof charges and T is the absolute temperature, the operation resistancewhen the current I is 1 mA becomes about 26Ω. This value is so small asto be neglected in comparison with the emitter resistance Re inserted ingeneral. Since the item of current I is not included in the formula (2),it can be understood from the formula (2) that gain does not change inthe circuit of FIG. 5 even when the current Iee is changed.

Meanwhile, the dynamic range of this amplifying circuit is ±kT/q=±26 mVwhen the emitter resistance Re0 is 0Ω, but it is enlarged up to Iee·REwhen the emitter resistance Re0 takes a finite value. Therefore, theamplifying circuit of this embodiment can change dynamic range whilekeeping the gain to a constant value by changing the current Iee.

The amplifying circuit which can vary dynamic range is never limited tothe circuit of FIG. 5 and it may be the circuit, for example, using Nchannel MOSFETs in place of the bipolar transistors Q1 to Q5 of FIG. 5and P channel MOSFETs in place of the transistors Q10 to Q13. Moreover,it is also possible to introduce the circuit, as illustrated in FIG. 6,where the dynamic range is changed by using the variable current sourcesVCS1, VCS2 as the current source in the emitter side of the emitterfollower transistors Qe1, Qe2 of the subsequent stage of thedifferential amplifying stage, and switching the currents of thevariable current sources VCS1, VCS2 by the circuit similar to thecurrent switching circuit 138 consisting of the constant current sourceCCS, transistors Q10 to Q13, Q21 to Q23 and the decoder DEC. In FIG. 6,CI1 and CI2 are constant current sources consisting of a transistorwhere a constant potential is applied to the base and a resistorconnected to the emitter of the same transistor.

The amplifying circuit which can change IPC, namely the dynamic rangehas been described above. In the embodiments illustrated in FIG. 1 toFIG. 3, the amplifying circuits 132, 136 are designed as the amplifyingcircuits which can vary the gain with the gain control voltage Vapc fromthe baseband circuit 140. Meanwhile, the amplifying circuit of FIG. 5fixes the gain thereof. Therefore, an example of the amplifying circuitof which gain is fixed will be described with reference to FIG. 7 andFIG. 8.

FIG. 7 and FIG. 8 illustrate examples of the variable gain amplifyingcircuit which is configured to change step by step the gain thereof. Thevariable gain amplifying circuit of FIG. 7 is provided with a pluralityof resistors Re11, Re12, . . . , Re1 n connected in parallel between theemitters of a couple of input differential bipolar transistorscorresponding to the Q1 and Q2 in the circuit of FIG. 5. These resistorsare connected or disconnected with the switches SW11, SW12; SW21, SW22,. . . , SWn1, SWn2.

Moreover, an AD converting circuit 139 for converting the gain controlvoltage Vapc from the baseband circuit 140 to a digital code is alsoprovided, the ON/OFF conditions of the switches SW11, SW12; SW21, SW22,. . . , SWn1, SWn2 are set with an output of this AD converting circuit139 and the gain can be varied depending on the combination of theswitches to set the ON condition. The resistors Re11, R312, . . . , Re1n may have the identical resistance value but the number of resistorsmay be reduced by forming these resistors, for example, to have theweight of 2×n.

The variable gain amplifying circuit of FIG. 7 operates as the amplifierhaving a small gain as the resistance value of resistor connectedbetween the emitter terminals of the differential bipolar transistorsQ1, Q2 is larger. Therefore, in the variable gain amplifying circuit ofthis embodiment, an output of the AD converting circuit 139 isdistributed to the switches SW11, SW12; SW21, SW22, . . . , SWn1, SWn2so that as the gain control voltage Vapc from the baseband circuit 140is larger, more switches are turned ON among the switches SW11, SW12;SW21, SW22; . . . , SWn1, SWn2, or as the gain control voltage Vapc ishigher, the switch corresponding to the resistor having smaller weightresistance is turned ON.

Here, VCS3, VCS4 are variable constant current sources consisting of theconstant current transistors Q3, Q4 and the emitter resistors Re1, Re2thereof. Although not illustrated in FIG. 7, the variable constantcurrent sources VCS3, VCS4 are configured to be switched in the currentthereof with the current switching circuit 138 of the structureidentical to that of FIG. 5 based on the control information MCindicating the number of multiplexes and to vary the dynamic range ofthe circuit. The switches SW11, SW12; SW21, SW22, . . . , SWn1, SWn2 mayalso be configured to realize the ON/OFF control with the signalobtained by decoding an output of the AD converting circuit 139 with adecoder provided, in place of direct ON/OFF control using an output ofthe AD converting circuit 139.

In the variable gain amplifying circuit of FIG. 8, the differentialbipolar transistors Q11, Q12; Q21, Q22, . . . , Qn1, Qn2 of a pluralityof sets forming pairs are connected and the resistors Re1, Re2, . . . ,Ren having identical or different resistance values to or from oneanother are respectively connected between the emitters of transistorsof each pair. Moreover, the emitters of the transistors Q11, Q12; Q21,Q22, . . . , Qn1, Qn2 are connected or isolated to or from the commoncurrent sources VCS2, VCS4 via the switches SW11, SW12; SW21, SW22, . .. , SWn1, SWn2. The transistors Q11, Q12; Q21, Q22, . . . , Qn1, Qn2 maybe formed in the same size or may be formed as the transistors ofdifferent emitter sizes.

The variable gain amplifying circuit of FIG. 8 operates as the amplifierof smaller gain as the smaller number of bipolar transistors areconnected to the switch to be turned ON, namely the current sourcesVCS3, VCS4, or the bipolar transistors connected to the current sourcesVCS3, VCS4 have the smaller emitter size.

Therefore, in the variable gain amplifying circuit of this embodiment,an output of the AD converting circuit 139 is distributed to theswitches SW11, SW12; SW21, SW22; . . . , SWn1, SWn2 so that as the gaincontrol voltage Vapc supplied from the baseband circuit 140 is higher,more switches are turned ON among the switches SW11, SW12; SW21, SW22, .. . , SWn1, SWn2, or as the gain control voltage Vapc is higher, theswitches corresponding to the transistor having larger emitter size areturned ON, otherwise, as the gain control voltage Vapc from the basebandcircuit 140 is lower, less switches are turned ON among the switchesSW11, SW12; SW21, SW22, . . . , SWn1, SWn2, or as the gain controlvoltage Vapc is lower, the switches corresponding to the transistorhaving smaller emitter size are turned ON.

Rc1, Rc2 are common collector resistors, and VCS3, VCS4 are variableconstant current sources. The dynamic range is made variable byswitching the current with the current switching circuit 138 based onthe control information MC indicating the number of multiplexes suppliedfrom the baseband circuit 140. The switches SW11, SW12; SW21, SW22, . .. , SWn1, SWn2 are controlled for ON and OFF with an output of the ADconverting circuit 139 for converting the output control voltage Vapcfrom the baseband circuit 140 into a digital code. The output controlvoltage from the baseband circuit 140 may be an analog voltage but it isalso possible that this output voltage is given with the digital code.

Moreover, in above embodiment, the dynamic range of the variable gainamplifying portions 132 and 136 may be varied but it is also possiblethat a mixer 135 illustrated in FIG. 1 and FIG. 3 is configured toswitch the operation current, the dynamic range can be varied byswitching the operation current of the mixer 135 based on the controlinformation MC indicating the number of multiplexes and therebydistortion of signal may be reduced by controlling increase of thecurrent consumption.

The other embodiment of the present invention will be described withreference to FIG. 9 and FIG. 10.

This embodiment varies the dynamic range of the first variable gainamplifying portion 132 and the second variable gain amplifying portion136 in the transmission circuit 130 based on the control information MCindicating the number of multiplexes supplied from the baseband circuit140 and also varies the dynamic range of the power amplifier (highfrequency power amplifying circuit) in the power module 120. FIG. 10shows a power amplifier circuit whose dynamic range is variable.

In the power amplifier illustrated in FIG. 10, three amplifying stages211, 212, 213 are cascade-connected via the impedance matching circuitsMN1 to MN3. In each amplifying stage, a field effect transistor forpower amplification (hereinafter, the field effect transistor isreferred to as FET) is provided and FIG. 10 illustrates a practicalcircuit structure of the final amplifying stage 213. Although notillustrated in the figure, the amplifying stages 211, 212 of the firstand second stages have the structure similar to that of the finalamplifying stage. MN4 is an impedance matching circuit connected betweenthe drain terminal of the FET of the final amplifying stage 213 and theoutput terminal OUT, while the matching circuits MN1 to MN4 arerespectively formed an inductance element and a capacitance elementconsisting of the microstrip line formed on the ceramic substrate.

The final amplifying stage 213 is formed of an FET 31 for poweramplification to receive an output of the preceding amplifying stage 212with the gate terminal via the impedance matching circuit MN3 and an FET32 current-Miller connected with the FET 31. A power source voltage Vddis impressed to the drain terminal of the FET 31 via an inductanceelement L3. Since the control current Ic3 supplied from the bias controlcircuit 230 is applied to the current Miller FET 32, the drain currentId which is identical to this current or is proportional to this currentis impressed to the FET 31. The amplifying stages 211, 212 of the firstand second stages are similarly constituted.

As described above, the signal Pout where the DC element of the highfrequency input signal Pin is cut and the AC element is amplified up tothe predetermined level can be outputted by controlling theamplification degree of each stage with the bias currents Ic1, Ic2, Ic3which are given to each amplifying stage 211 to 213 by the bias controlcircuit 230. The control signals Ic1, Ic2, Ic3 are generated by the biascontrol circuit 230 depending on the gain control voltage Vapc suppliedfrom the baseband circuit 140 to provide the predetermined output powerwith the amplifying stages 211 to 213 as a whole.

In this embodiment, a plurality of FETs 32, . . . , FET3 n are connectedin parallel to the FET 31 of the final amplifying stage 213, and thechange-over switches SW32, . . . , SW2 n are provided between the gateterminals of these FET 32, . . . , FET 3 n and the gate terminal of theFET 31. The FETs 32, . . . , FET 3 n are formed as the element in thesize (gate width) which is smaller than the FET 31. The switches SW 31,. . . , SW 3 n are controlled with an output of the decoder DEC fordecoding the control information MC indicating the number of multiplexesfrom the baseband circuit 140 and are configured to selectively impressthe voltage identical to the gate voltage of the FET 31 or the groundingvoltage to the gate terminals of the FET 32, . . . , FET 3 n. Under thecondition that all switches SW 31, . . . , SW 3 n are changed over tothe side to impress the ground potential to the gate terminals of theFET 32, . . . , FET 3 n, only the FET 31 performs the amplifyingoperation. When the number of switches changed over to the side toimpress the voltage identical to the gate voltage of the FET 31 to thegate terminals of the FET 32, ..., FET 3 n increases, a drain current ofthe final amplifying stage 213 increases to expand the dynamic range.

In this embodiment, the gain is also increased a little by increasingthe drain current of the final amplifying stage 213, the greater part ofthe gain required for the power amplifier 210 as a whole is attainedwith the first and second amplifying stages 211, 212, and the FET 31 ofthe final stage is designed to operate in the manner that thepredetermined output power can be obtained by applying a current whenthe gain (voltage gain) is almost equal to “1”. Accordingly, only thedynamic range can be widened while the gain is kept almost to theconstant value by increasing the drain current of the finals stagedepending on the multiplex number information MC. Moreover, in the casewhere the gain changes exceeding the allowable value by increasing thedrain current to the final amplifying stage, the control may be realizedto change, in the reverse direction, the gain of the first and secondamplifying stages depending on such change of the gain.

Moreover, in the embodiment of FIG. 10, the dynamic range is madevariable by providing a plurality of FET 32, . . . , FET 3 n in parallelto the FET 31 of the final amplifying stage 213. However, it is alsopossible, as illustrated in FIG. 11, to form the circuit to change thedynamic range, by providing the current source CCS3 to give the biascurrent Ic3 of the FET 31 of the final amplifying stage 213 as thevariable current source, and varying the drain current of the FET 31 byswitching the current Ic3 of the variable current source with thecircuit similar to the current switching circuit 138 consisting of theconstant current source CCS, transistors Q10 to Q13, Q21 to Q23 and thedecoder DEC of FIG. 5.

As the power amplifying transistor 31 of the final stage and thetransistors of the first and second amplifying stages, FETs are used inthe embodiments of FIG. 10 and FIG. 11. However, it is also possible touse the other transistors such as bipolar transistor, GaAsMESFET,hetero-junction bipolar transistor (HBT), HEMT (High Electron MobilityTransistor) or the like.

The preferred embodiments of the present invention have been describedbut the present invention is never limited thereto and naturally allowsvarious changes and modifications within the scope not departing fromthe claims thereof. For example, in the embodiments described above, themaximum number of multiplexes is set to “6”, the control informationindicating the number of multiplexes is formed of three bits, and thedynamic range of the amplifying circuit is changed in seven steps basedon the control information of three bits. However, the present inventioncan also be applied when the control information indicating the numberof multiplexes is formed of two bits or four or more bits. When thecontrol information indicating the number of multiplexes is formed offour or more bits, the number of transistors which are connected withthe transistor Q10 with the current-Miller connection is increased.

Moreover, even in the mobile telephone of the W-CDMA system wherein themaximum number of multiplexes is set to “6” and the control informationindicating the number of multiplexes is formed of three bits, it is notalways required to switch the operation current of the amplifyingcircuit depending on the number of multiplexes as described. The currentmay be switched in two stages with the procedures such that, forexample, as will be understood from FIG. 14, since the peak factorincreases suddenly when the number of multiplexes shifts to “3” from“2”, it is also possible that the number of transistors connected to thetransistor Q10 with the current-Miller connection method in the currentswitching circuit 138 as illustrated in FIG. 5 is set to two in place ofthree, the current is applied only one of the two current-Millertransistors when the number of multiplexes is “2” or less, and theoperation current of the amplifying circuit is increased by applying thecurrent to both current- Miller transistors when the number ofmultiplexes is set to “3” or more.

In addition, in above embodiments, the control signal MC indicating thenumber of multiplexes is supplied to the code division multiplextransmission circuit 130 from the baseband circuit 140. However, in thesystem comprising a controller such as a microprocessor for totallycontrolling the system in addition to the baseband circuit, it is alsopossible to form the structure to give the control information MCindicating the number of multiplexes to the code division multiplextransmission circuit 130 and power module 120 from the controller.

In above description, the present invention has been applied to themobile telephone which enables communication by the W-CDMA system whichis the major application field thereof and also the RF-IC as thesemiconductor integrated circuit for communication to be introduced intothe above mobile telephone. But the present invention is never limitedthereto and can also be generally used for the mobile telephone of thecommunication system which realizes multiplexing by spectrum diffusionsuch as the dual-mode mobile telephone which enables communication withthe cdma 2000 system and two systems of the W-CDMA system and PDC systemfor the mobile telephone.

In addition, an example for switching the operation current has beendescribed in the embodiments described above, but it is also possible tolinearly change the operation current depending on the number ofmultiplexes. Namely, it is enough that the operation current is changeddepending on the number of multiplexes.

The effects of the typical inventions disclosed in the present inventionare as follow.

Namely, in the wireless communication system which realizes multiplexingby spectrum diffusion such as the W-CDMA system, if the number ofmultiplexes increases, the signal can be transmitted without anydistortion and current consumption when the number of multiplexes issmall can also be reduced. Accordingly, when the present invention isapplied to the mobile telephone which is operated with a battery, theoperation life of battery, namely the maximum communication time andmaximum waiting time with single charging process can be extended.

Moreover, according to the present invention, since the 1 dB compressionpoint ICP in the variable gain amplifying portion of the transmissioncircuit may be improved, it is also possible to attain the semiconductorintegrated circuit device for communication use ensuring excellentcharacteristic of leak power ratio on the adjacent channels ACPR and thewireless communication system utilizing the same device.

1. A semiconductor integrated circuit device for wireless communicationapparatus comprising: modulation means for modulating multiplexedsignals; and amplification means for amplifying modulated signals fromthe modulation means, wherein the amplification means receives a firstcontrol information for instructing a amplification gain and a secondcontrol information for indicating the number of multiplexes of themultiplexed signals, and wherein a operation current of theamplification means is controlled to increase the operation current inaccordance with the number of multiplexes is large or to decrease saidoperation current in accordance with the number of multiplexes is small.2. The semiconductor integrated circuit device for wirelesscommunication apparatus according to claim 1, wherein said secondcontrol information is formed of a plurality of bits, and the operationcurrent of the amplification means can be changed by the signal decodedthe second control information.
 3. The semiconductor integrated circuitdevice for wireless communication apparatus according to claim 2,wherein the amplification means includes a pair of input differentialtransistors and a first transistor connected in series to each of thepair of input differential transistors, and wherein the operationcurrent is controlled in accordance with a current flowing into a secondtransistor which is connected to the first transistor with thecurrent-Miller connection is changed by the second control information.4. The semiconductor integrated circuit device for wirelesscommunication apparatus according to claim 3, wherein the amplificationmeans comprises a plurality of resistance elements provided in parallelbetween emitter terminals of the pair of differential transistors and aplurality of switch elements for connecting and disconnecting theresistance elements, and the gain of the amplification means is changedwhen said switch elements are turned ON or OFF depending on said firstcontrol information to connect or disconnect said resistance elements.5. The semiconductor integrated circuit device for wirelesscommunication apparatus according to claim 3, wherein the amplificationmeans comprises a plurality of pairs of differential transistorsprovided in parallel to said pair of differential transistors, and thegain of the amplification means is varied when said plural pairs ofdifferential transistors are connected or disconnected depending on saidfirst control information.
 6. A wireless communication apparatuscomprising: a semiconductor integrated circuit device including amodulation means for modulating multiplexed signal, and an amplificationmeans for amplifying modulated signals from the modulation means,wherein the amplification means receives a first control information forinstructing a amplification gain and a second control information forindicating the number of multiplexes of the multiplexed signals, andwherein a operation current of the amplification means is controlled toincrease the operation current in accordance with the number ofmultiplexes is large or to decrease said operation current in accordancewith the number of multiplexes is small; a baseband circuit forsupplying the multiplexed signals to the modulation means; and anelectronic component including a power amplifier for amplifying thesignal outputted from the semiconductor integrated circuit device, and abias circuit for giving bias to the power amplifier in accordance withthe first control information, wherein the first control information andthe second control information is supplied from the baseband circuit.